Performance Analysis of MIMO-OFDM System Using QOSTBC Code Structure for M-PSK

Lavish Kansal, Ankush Kansal & Kulbir Singh
Signal Processing: An International Journal (SPIJ), Volume (5) : Issue (2) : 2011 19
Performance Analysis of MIMO-OFDM System Using QOSTBC
Code Structure for M-PSK
Lavish Kansal lavish.s690@gmail.com
Electronics and Communication Engineering
Department Thapar University
Patiala (147004), INDIA
Ankush Kansal akansal@thapar.edu
Kulbir Singh ksingh@thapar.edu
Abstract
MIMO-OFDM system has been currently recognized as one of the most competitive technology
for 4G mobile wireless systems. MIMO-OFDM system can compensate for the lacks of MIMO
systems and give play to the advantages of OFDM system. In this paper, a general Quasi
orthogonal space time block code (QOSTBC) structure is proposed for multiple-input multiple-
output–orthogonal frequency-division multiplexing (MIMO-OFDM) systems for 4X4 antenna
configuration. The signal detection technology used in this paper for MIMO-OFDM system is
Zero-Forcing Equalization (linear detection technique).
In this paper the analysis of high level of modulations (i.e. M-PSK for different values of M) on
MIMO-OFDM system is presented. Here AWGN and Rayleigh channels have been used for
analysis purpose and their effect on BER for high data rates have been presented. The proposed
MIMO-OFDM system with QOSTBC using 4X4 antenna configuration has better performance in
terms of BER vs SNR than the other systems.
Keywords: MIMO, OFDM, QOSTBC, M-PSK
1. INTRODUCTION
As the demand for high-data rate multimedia grows, several approaches such as increasing
modulation order or employing multiple antennas at both transmitter and receiver have been
studied to enhance the spectral efficiency. [1][2] In today’s communication systems Orthogonal
Frequency Division Multiplexing (OFDM) is a widespread modulation technique. Its benefits are
high spectral efficiency, robustness against inter-symbol interference, ease of implementation
using the fast Fourier transform (FFT) and simple equalization techniques. Recently, there have
been a lot of interests in combining the OFDM systems with the multiple-input multiple-output
(MIMO) technique. These systems are known as MIMO OFDM systems.
Spatially multiplexed MIMO is known to boost the throughput, on the other hand, when much
higher throughputs are aimed at, the multipath character of the environment causes the MIMO
channel to be frequency-selective. OFDM can transform such a frequency-selective MIMO
channel into a set of parallel frequency-flat MIMO channels and also increase the frequency

efficiency. Therefore, MIMO-OFM technology has been researched as the infrastructure for next
generation wireless networks. [3]
Therefore, MIMO-OFDM, produced by employing multiple transmit and receive antennas in an
OFDM system has becoming a practical alternative to single carrier and Single Input Single
Output (SISO) transmission.[4] However, channel estimation becomes computationally more
complex compared to the SISO systems due to the increased number of channels to be
estimated. This complexity problem is further compounded when the channel from the ith transmit
antenna to the mth receive antenna is frequency-selective. Using OFDM, information symbols are
transmitted over several parallel independent sub-carriers using the computationally efficient
IFFT/FFT modulation/demodulation vectors. [5]-[8]
These MIMO wireless systems, combined with OFDM, have allowed for the easy transmission of
symbols in time, space and frequency. In order to extract diversity from the channel, different
coding schemes have been developed. The seminal example is the Alamouti Space Time Block
(STB) code [9] which could extract spatial and temporal diversity. Many other codes have also
been proposed [10]–[12] which have been able to achieve some or all of the available diversity in
the channel at various transmission rates.
In open-loop schemes, there are generally two approaches to implement MIMO systems. One is
to increase the spatial transmit diversity (STD) by means of space-time coding and space-
frequency coding. Another is to raise the channel capacity by employing spatial division
multiplexing (SDM) that simultaneously transmits independent data symbols through multiple
transmit antennas. STD mitigates impairments of channel fading and noise, whereas SDM
increases the spectral efficiency. [13][14]
In section 2, general theory of OFDM and the necessary condition for orthogonality is discussed.
In section 2.1, the signal model of OFDM system with SISO configuration is discussed in detail
with the help of block diagram. In section 2.2, M-PSK (M-Phase Shift Keying) modulation
technique is discussed in detail. In section 2.3, different channels used for analyses purpose are
discussed namely AWGN and Rayleigh channel. In section 3, general theory about the MIMO
system is presented. In section 4, MIMO-OFDM system with QOSTBC is discussed. In section
4.1, general theory about QOSTBC and the proposed QOSTBC code structure for 8x8 antenna
configuration is presented. In section 4.2, idea about the linear detection technique i.e. Zero
Forcing equalization for MIMO-OFDM system is presented. Finally in section 5, the simulated
results based on the performance of MIMO-OFDM system in AWGN and Rayleigh channels have
been shown in the form of plots of BER vs SNR for M-PSK modulation and for different antenna
configurations.
2. ORTHOGONAL FREQUENCY DIVISION MULTIPLEXING (OFDM)
OFDM is a multi-carrier modulation technique where data symbols modulate a sub-carrier which
is taken from orthogonally separated sub-carriers with a separation of ‘fk’ within each sub-carrier.
Here, the spectra of sub-carrier is overlapping; but the sub-carrier signals are mutually
orthogonal, which is utilizing the bandwidth very efficiently. To maintain the orthogonality, the
minimum separation between the sub-carriers should be ‘fk’ to avoid ICI (Inter Carrier
Interference).
By choosing the sub-carrier spacing properly in relation to the channel coherence bandwidth,
OFDM can be used to convert a frequency selective channel into a parallel collection of
frequency flat sub-channels. Techniques that are appropriate for flat fading channels can then be
applied in a straight forward fashion .

2.1 OFDM Signal Model
Figure.1 shows the block diagram of a OFDM system with SISO configuration. Denote Xl ( l =
0,1,2,....,N −1) as the modulated symbols on the lth transmitting subcarrier of OFDM symbol at
transmitter, which are assumed independent, zero-mean random variables, with average power
.
The complex baseband OFDM signal at output of the IFFT can be written as:
xn = l (1)
where N is the total number of subcarriers and the OFDM symbol duration is T seconds.
FIGURE 1: Block Diagram of OFDM system
At the receiver, the received OFDM signal is mixed with local oscillator signal, with the frequency
offset deviated from Δf the carrier frequency of the received signal owing to frequency estimation
error or Doppler velocity, the received signal is given by:
n = (xn hn) + zn (2)
where hn, , and zn represent the channel impulse response, the corresponding frequency
offset of received signal at the sampling instants: Δf T is the frequency offset to subcarrier
frequency spacing ratio, and the AWGN respectively, while denotes the circular convolution.
Channel
Coding
Inter
leaving
Modulation S
/
P
I
F
F
T
P
/
S
Cyclic
Prefix
CHANNEL
Remove
Cyclic
Prefix
S
/
P
F
F
T
P
/
S
Demodulation De-Inter
leaving
Channel
Decoding
Source
Data
Receive
Data

Assuming that a cyclic prefix is employed; the receiver have a perfect time synchronization. Note
that a discrete Fourier transform (DFT) of the convolution of two signals in time domain is
equivalent to the multiplication of the corresponding signals in the frequency domain.
Then the output of the FFT in frequency domain signal on the kth receiving subcarrier becomes:
k = lHlYl - k + Zk , k=0,….,N-1
= XkHkU0 + HlYl - k + Zk (3)
The first term of (3) is a desired transmitted data symbol Xk. The second term represents the ICI
from the undesired data symbols on other subcarriers in OFDM symbol. Hk is the channel
frequency response and Zk denotes the frequency domain of zn. The term Yl - k is the coefficient of
FFT (IFFT), is given by:
Yl - k = (4)
when the channel is flat, Yl - k can be considered as a complex weighting function of the
transmitted data symbols in frequency domain. [15]
2.2 Different Modulations Techniques Used in OFDM System
Modulation is the process of mapping the digital information to analog form so it can be
transmitted over the channel. Consequently every digital communication system has a modulator
that performs this task. Closely related to modulation is the inverse process, called demodulation,
done by the receiver to recover the transmitted digital information. [16]
Modulation of a signal changes binary bits into an analog waveform. Modulation can be done by
changing the amplitude, phase, and frequency of a sinusoidal carrier. There are several digital
modulation techniques used for data transmission. The nature of OFDM only allows the signal to
modulate in amplitude and phase.
There can be coherent or non-coherent modulation techniques. Unlike non-coherent modulation,
coherent modulation uses a reference phase between the transmitter and the receiver which
brings accurate demodulation together with receiver complexity. [17]
2.2.1 Phase Shift Keying
Phase-shift keying (M-PSK) for which the signal set is:
Si(t)= *(cos (2π*fc + 2 )) (5)
i=1,2,…..M & 0 < t < Ts
where Es the signal energy per symbol Ts is the symbol duration, and fc is the carrier frequency.
This phase of the carrier takes on one of the M possible values, namely
θi = 2(i-1)π/M where i=1,2,…,M
An example of signal-space diagram for 8-PSK is shown in figure 2

FIGURE 2 : Signal-space diagram for 8-PSK
2.3 CHANNELS
Wireless transmission uses air or space for its transmission medium. The radio propagation is not
as smooth as in wire transmission since the received signal is not only coming directly from the
transmitter, but the combination of reflected, diffracted, and scattered copies of the transmitted
signal.
Reflection occurs when the signal hits a surface where partial energy is reflected and the
remaining is transmitted into the surface. Reflection coefficient, the coefficient that determines the
ratio of reflection and transmission, depends on the material properties.
Diffraction occurs when the signal is obstructed by a sharp object which derives secondary
waves. Scattering occurs when the signal impinges upon rough surfaces, or small objects.
Received signal is sometimes stronger than the reflected and diffracted signal since scattering
spreads out the energy in all directions and consequently provides additional energy for the
receiver which can receive more than one copies of the signal in multiple paths with different
phases and powers. Reflection, diffraction and scattering in combination give birth to multipath
fading. [18]
2.3.1 AWGN Channel
Additive white Gaussian noise (AWGN) channel is a universal channel model for analyzing
modulation schemes. In this model, the channel does nothing but add a white Gaussian noise to
the signal passing through it. This implies that the channel’s amplitude frequency response is flat
(thus with unlimited or infinite bandwidth) and phase frequency response is linear for all
frequencies so that modulated signals pass through it without any amplitude loss and phase
distortion of frequency components. Fading does not exist. The only distortion is introduced by
the AWGN. AWGN channel is a theoretical channel used for analysis purpose only.
The received signal is simplified to:
r(t) = s(t) + n(t) (6)
where n(t) is the additive white Gaussian noise. [18]
2.3.2 Rayleigh Fading Channel
Constructive and destructive nature of multipath components in flat fading channels can be
approximated by Rayleigh distribution if there is no line of sight which means when there is no
direct path between transmitter and receiver. The received signal can be simplified to:

r(t) = s(t)*h(t) + n(t) (7)
where h(t) is the random channel matrix having Rayleigh distribution and n(t) is the additive
white Gaussian noise. The Rayleigh distribution is basically the magnitude of the sum of two
equal independent orthogonal Gaussian random variables and the probability density function
(pdf) given by:
p(r) = 0 (8)
where σ2
is the time-average power of the received signal. [19][20]
3. MULTI INPUT MULTI OUTPUT (MIMO) SYSTEMS
Multi-antenna systems can be classified into three main categories. Multiple antennas at the
transmitter side are usually applicable for beam forming purposes. Transmitter or receiver side
multiple antennas for realizing different (frequency, space) diversity schemes. The third class
includes systems with multiple transmitter and receiver antennas realizing spatial multiplexing
(often referred as MIMO by itself).
In radio communications MIMO means multiple antennas both on transmitter and receiver side of
a specific radio link. In case of spatial multiplexing different data symbols are transmitted on the
radio link by different antennas on the same frequency within the same time interval. Multipath
propagation is assumed in order to ensure the correct operation of spatial multiplexing, since
MIMO is performing better in terms of channel capacity in a rich scatter multipath environment
than in case of environment with LOS (line of sight). This fact was spectacularly shown in [21].
MIMO transmission can be characterized by the time variant channel matrix:
H( ) = (9)
where the general element, hnt,nr (τ, t) represents the complex time-variant channel transfer
function at the path between the nt-th transmitter antenna and the nr-th receiver antenna. NT and
NR represent the number of transmitter and receiver antennas respectively.
Derived from Shannon’s law, for the capacity of MIMO channel the following expression was
proven in [21] and [22]:
C = (det (I + H Rss HH)) (10)
where H denotes the channel matrix and HH its transpose conjugate, I represents the identity
matrix and Rss the covariance matrix of the transmitted signal s.

Transmitting antennas MIMO-channels Receiving antennas
Tx 1 Rx 1
Tx 2 Rx 2
Tx M Rx N
FIGURE 3: Block Diagram of a generic MIMO system with M transmitters and N receivers
4. MIMO-OFDM WITH QUASSI ORTHOGONAL SPACE TIME BLOCK
CODING (QOSTBC)
MIMO-OFDM systems with orthogonal space–time block coding (O-STBC) [12] are particularly
attractive due to the fact that they require a relatively simple linear decoding scheme while still
providing full diversity gain . Unfortunately, they suffer from a lower code rate when a complex
signal constellation and the complexity that more than two transmit antennas are used. To
overcome the disadvantages of O-STBC, quasi-orthogonal space–time block coding (QO-STBC)
was proposed in the literature [23]-[24] and the existing works have shown that QO-STBC offers
a higher data rate and partial diversity gain.
To design a QO-STBC with full diversity gain, an improved QO-STBC through constellation
rotation was proposed in [25] and [26].Maximum-likelihood (ML) decoding in QO-STBC works
with pairs of transmitted symbols, leading to an increase in decoding complexity with modulation
level M2. This subsequently increases transmission delay when a high-level modulation scheme
or multiple antennas are employed. Sung et al. [27] proposed a method to improve the QO-STBC
performance with iterative decoding, which of course achieves higher reliability but increases
decoding complexity. In [28]–[32], some new decoding methods were proposed to reduce the
computational complexity.
4.1 Quassi Orthogonal Space Time Block Codes
Consider a system with eight transmit antennas (i.e. M = 4) and 4 receive antennas (i.e. N=4). In
what follows, assume that perfect channel state information (CSI) is available at the receiver but
unavailable at the transmitter. Also assume that the channel is quasi-static, i.e. the channel
coefficients are constant within one block of code transmission and independently realized from
block to block. Let A12 and A34 be Alamouti code as in [9]
A12 = and A34 =
Here the subscript 12 and 34 are used to represent the indeterminate s1, s2, s3 and s4 in the
transmission matrix. Now consider the space time block code for M and N equals to 4 according
the method given in [24], the matrix for 4X4 antenna configuration can also be constructed as
follows :
B = = (11)
Note that it has been proven in [33] maximum diversity of the order of 4*N for a rate one code is
impossible in this case. Now, suppose Vi, i = 1 ,2…..4 as the ith column of Q, it is easy to see that

(12)
Where = is the inner product of vectors Vi and Vj . Therefore, the subspace
created by V1 and V4 is orthogonal to the subspace created by V2 and V3 , and similar is true for
other columns as given by equation(11).
4.2 Signal Detection of Mimo-ofdm System
Signal detection of MIMO-OFDM system can be carried out by various sub-carrier channel signal
detection. Although the whole channel is a frequency-selective fading, but various sub-carriers
channel divided can be regarded as flat fading, so the flat fading MIMO signal detection algorithm
for MIMO-OFDM system can be directly into the detection of all sub-channels, and signal
detection algorithm of the corresponding MIMO-OFDM system can be obtained. Similarly, the
other optimization algorithms used in flat fading MIMO signal detection can also be leaded into
the MIMO-OFDM system. MIMO-OFDM detection methods consist of linear and nonlinear
detection test.
4.2.1 Zero Forcing Algorithm [34]
Zero Forcing algorithm is regard the signal of each transmitting antenna output as the desired
signal, and regard the remaining part as a disturbance, so the mutual interference between the
various transmitting antennas can be completely neglected. The specific algorithm is as follows:
For k = 0, 1, 2,………….,K-1, so that,
R(k) = [R1(k),R2(k),…….……..,RN(k)]T (13)
S(k) = [S1(k),S2(k),…………….,SM(k)]T (14)
N(k) = [N1(k),N2(k),……...……,NN(k)]T (15)
H(k) = (16)
Here R(k), S(k), N(k) respectively express output signal, the input signal and noise vector of the k
sub-channels in MIMO-OFDM system, for M transmitting antennas and N receiving antennas,
H(k) expresses channel matrix of the k sub-channels, mathematical expression of sub-channel in
the MIMO-OFDM system is as follows:

R(k) = H(k)S(k) + N(k) (17)
S1(k) R1(k) (k)
S2(k) R2(k) (k)
SM(k) RN(k) (k)
FIGURE 4: Baseband block diagram of k subcarrier channel in MIMO-OFDM system
There is a linear relationship between input signal S(k) and output signal R(k), that is similar to
the flat fading channel for each subcarrier channel in MIMO-OFDM system. Its equivalent block
diagram is shown in Figure 4. Therefore, signal detection can be transformed into K sub-channels
in their signal detection to complete in MIMO-OFDM system and each sub-channel detection of
the above can be used flat fading MIMO channel to achieve the detection algorithm.
Zero-forcing (ZF) detection algorithm for MIMO detection algorithm is the most simple and basic
algorithms, and the basic idea of zero forcing algorithm is get rid of MIMO-channel interference by
multiplying received signal and the inverse matrix of channel matrix. Zero-Forcing solution of
MIMO-OFDM system is as follows:
SZF = H-1 R = S + H-1 N (18)
In which H-1 is the channel matrix for the generalized inverse matrix, the type is obtained for hard-
decision demodulation after that to be the source signal estimates:
ZF = E(SZF) (19)
5. SIMULATION RESULTS DISCUSSIONS
The system discussed above has been designed and results are shown in the form of SNR vs
BER plot for different modulations and different channels. Here different antenna configurations
such as 1x1, 2x2 are used to show the advantage in term of SNR of using 4X4 antenna
configuration over the other configurations. The analyses have been done for three channels
AWGN and Rayleigh channel.
Sub-
carrier
channel
H(k)
Sub-
channel
detection
Channel
Estimation

0 10 20 30 40 50 60 70 80 90
10
-3
10
-2
10
-1
10
0
signal to noise ratio
biterrorrate
SNR vs BER plot for MIMO-OFDM FOR 32-PSK in AWGN channel
1 TX x 1 RX
2 TX x 2 RX
4 TX x 4 RX
FIGURE 5: (a)
0 10 20 30 40 50 60 70 80 90
10
-3
10
-2
10
-1
10
0
biterrorrate
1 TX x 1 RX
2 TX x 2 RX
4 TX x 4 RX
FIGURE 5: (b)
0 10 20 30 40 50 60 70 80 90
10
-3
10
-2
10
-1
10
0
biterrorrate
1 TX x 1 RX
2 TX x 2 RX
4 TX x 4 RX
FIGURE 5: (c)
0 10 20 30 40 50 60 70 80 90
10
-3
10
-2
10
-1
10
0
biterrorrate
1 TX x 1 RX
2 TX x 2 RX
4 TX x 4 RX
FIGURE 5: (d)
0 10 20 30 40 50 60 70 80 90
10
-3
10
-2
10
-1
10
0
biterrorrate
1 TX x 1 RX
2 TX x 2 RX
4 TX x 4 RX
FIGURE 5: (e)
Figure 5 (a)-(e): SNR vs BER plots for PSK
over AWGN channel for MIMO-OFDM system
employing different antenna configurations (a)
32-PSK (b) 64-PSK (c) 128-PSK (d) 256-PSK
(e) 512-PSK.
SNR vs BER plots for M-PSK over AWGN channel for MIMO-OFDM system employing different antenna
configurations are presented in Figure 5. Here the graph depicts that in MIMO-OFDM system as we goes
on increasing the no. of Transmitters and Recievers the BER keeps on decreasing due to space diversity
and the proposed system provide better BER performance as compared to the other antenna
configurations.

0 10 20 30 40 50 60 70 80 90
10
-3
10
-2
10
-1
10
0
biterrorrate
SNR vs BER plot for MIMO-OFDM FOR 32-PSK in RAYLEIGH channel
1 TX x 1 RX
2 TX x 2 RX
4 TX x 4 RX
FIGURE 6: (a)
0 10 20 30 40 50 60 70 80 90
10
-3
10
-2
10
-1
10
0
biterrorrate
1 TX x 1 RX
2 TX x 2 RX
4 TX x 4 RX
FIGURE 6: (b)
0 10 20 30 40 50 60 70 80 90
10
-3
10
-2
10
-1
10
0
biterrorrate
1 TX x 1 RX
2 TX x 2 RX
4 TX x 4 RX
FIGURE 6
(c)
0 10 20 30 40 50 60 70 80 90
10
-3
10
-2
10
-1
10
0
biterrorrate
1 TX x 1 RX
2 TX x 2 RX
4 TX x 4 RX
FIGURE 6: (d)
0 10 20 30 40 50 60 70 80 90
10
-3
10
-2
10
-1
10
0
biterrorrate
1 TX x 1 RX
2 TX x 2 RX
4 TX x 4 RX
FIGURE 6: (e)
Figure 6 (a)-(e): SNR vs BER plots for PSK
over Rayleigh channel for MIMO-OFDM system
employing different antenna configurations (a)
32-PSK (b) 64-PSK (c) 128-PSK (d) 256-PSK
(e) 512-PSK.
In Figure 6 SNR vs BER plots for M-PSK over Rayleigh channel for MIMO-OFDM system employing
different antenna configurations are presented. It can be concluded from the graphs that in MIMO-
OFDM system as we goes on increasing the no. of Transmitters and Recievers the BER keeps on
decreasing due to space diversity and the proposed system provide better BER performance as
compared to the other antenna configurations. But here BER is greater than the AWGN channel.

Table 1 shows the improvement in terms of decibels shown by proposed system employing QOSTBC
code structure for 4X4 antenna configuration over the system employing QOSTBC code structure for 2X2
antenna configuration for different modulation schemes over different environments (channels).
Different
Modulations
For AWGN
Channel
For Rayleigh
Channel
32-PSK 3.22 dB 3.85 dB
64-PSK 5.02 dB 3.42 dB
128-PSK 4.75 dB 3.88 dB
256-PSK 6.5 dB 4.98 dB
512-PSK 3.42 dB 3.05 dB
TABLE 1: Table showing the improvement in terms of dB, by using the proposed QOSTBC code
structure (for 4X4 antenna configuration) for different Modulations and for different Channels.
7. CONCLUSION
In this paper, an idea about the performance of the MIMO-OFDM systems at higher modulation levels
and for different antenna configurations is presented. MIMO-OFDM system can be implemented using
higher order modulations to achieve large data capacity. But there is a problem of BER (bit error rate)
which increases as the order of the modulation increases. The solution to this problem is to increase the
value of the SNR so, that the effect of the distortions introduced by the channel will also goes on
decreasing, as a result of this, the BER will also decreases at higher values of the SNR for high order
modulations.
The motive of using high order antenna configuration (4X4) is to increase the space diversity, which will
automatically lower the BER at given SNR as compared to lower order Antenna configuration (1x1, 2x2).
By doing so, higher data capacity at any given SNR can be achieved. The proposed MIMO-OFDM system
with 4X4 antenna configuration provides better performance in terms of SNR as compared to the MIMO-
OFDM system with 2X2 antenna configuration at a BER of 10
-2
.
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